CMOS Devices PN junctions and diodes NMOS and

CMOS Devices • • • PN junctions and diodes NMOS and PMOS transistors Resistors Capacitors Inductors Bipolar transistors

The MOS Transistors

The MOS Transistors

CMOS Device Model • Objective – Hand calculations for analog design – Non-idealities and their effects – Efficient and accurate simulation • CMOS transistor models – Large signal model – Small signal model – Simulation model – Noise model

Good for VDS <VGS -VTH After that, ID become saturated.

Linear in deep triode Pro: voltage control of resistivity. Con: nonlinear resistor. As v. DS 0, ron

MOST Regions of Operation • Cut-off, or non-conducting: v. GS <VT – i. D=0 approximately • Conducting, or on: v. GS >=VT – Saturation: v. DS > v. GS – VT – Triode or linear or ohmic or non-saturation: v. DS <= v. GS – VT Saturation voltage:

With channel length modulation

i. D vs v. DS for several VGS gds gm*DVGS

Influence of Channel Length on l Lmin = 0. 25 Johns and Martin book gives an approximate formula with l 1/L At >=2*Lmin, l is small, Ro is large After 1 um, l remains about the same

Influence of VBS changes threshold voltage, and hence changes i-v curve.

Temperature Dependence of Mobility Linear Temperature Dependence of threshold voltage Saturation Velocity Junction capacitance Barrier potential

This is nonlinear if Vbs is temperature dependent

0. 35 um process ZTC biasing Referenced from Filanovsky’s paper

Reality: no single point crossing ID Not just one single crossing In AMI 0. 6 process Test on a single NMOS biased with fixed Vgs and Vds Vgs

AMI 0. 6 To refine the value. Vgs=1. 12 V Vgs=1. 14 V Optimum curve TC = 41 ppm/C Vgs=1. 17 V

Generic 018 Vgs=0. 717 V TC=27 ppm/C Vgs=0. 721 V Vgs=0. 727 V

Large signal model for approximate hand caculation

Capacitors Of The MOSFET

Capacitors in Cutoff

Capacitors in Saturation

Capacitors in Triode

Small signal model

Typically: VDB, VSB are in such a way that there is a reversely biased pn junction. Therefore: gbd ≈ gbs ≈ 0

In saturation: But

Intrinsic DC voltage gain: gm/gds = gm*rds

In non-saturation region

Intrinsic gain For large gain, use small ID or small over drive voltage, or in moderate to weak inversion.

High Frequency Figure of Merit w. T • • • AC current source input to G AC short S, D, B to gnd (i. e. constant voltages) Measure AC drain current output Calculate current gain Find frequency at which current gain = 1. Ignore rs and rd, Cbs, Cbd, gds, gbd all have zero voltage drop and hence zero current • Vgs = Iin /jw(Cgs+Cgb+Cgd) ≈ Iin /jw(Cgs+Cgd) • Io = − (gm − jw. Cgd)Vgs ≈ − gm Iin /jw(Cgs+Cgd) • |Io/Iin| = |gm − jw. Cgd|/w(Cgs+Cgd) ≈ gm/w(Cgs+Cgd)

amplification |Io/Iin| 0 d. B attenuation w. T w

• At w. T, current gain =1 • w. T ≈ gm/(Cgs+Cgd)≈ gm/Cgs • or

For fastest operation, use Vod near but before f. T peak For power efficiency, use Vod before f. T corner

High Frequency Figures of Merit wmax • • AC current source input to G AC short S, B to gnd Measure AC power into the gate Assume complex conjugate load Compute max power delivered by the transistor Find maximum power gain Find frequency at which power gain = 1.

gdo vs gm in short channel

gdo vs gm in short channel

Insights: • gdo increases all the way with current density Iden • gm saturates when Iden larger than 100 m. A/mm – Velocity saturation, mobility degradation ---short channel effects – Low gm/current efficiency – High linearity • For power efficiency and gm efficiency – Use moderate to low current density – Use small over drive voltage

To Av: (W/L), m, ID, l, set Vo. Q at mid rail For high speed: Veff, m; L, Cgd, rg For better linearity: Vds, Vdb, set Vo. Q at mid rail Veff range: <~0. 5 V; or <~0. 3 V for efficiency ID/W range: <100 m. A/mm; or <40 m. A/mm for efficiency

Intrinsic voltage gain of MOSFET Sweep V 1 Measure vgs Intrinsic voltage gain = gm/go = Dvds/Dvgs for constant Id

Weak inversion • When VGS is reduced to Vth, the drain current does not go to zero – It does not follow square law – It does not follow exponential law • When VGS is markedly below Vth, the drain current becomes an exponential function of VGS. – Behaves very much like a diode

A model from weak to strong inv

In strong inversion, n is about 1

In weak inversion

In weak inversion If vt = 25 m. V, n=2, gm/ID = 20 n=1. 5, gm/ID = 27 n=1. 2, gm/ID = 33

ID vs VGS Exponential model Square law model simulation

ID/(W/L) vs VG is sensitive to VBS

gm/ID vs VG is also sensitive to VBS

But gm/ID vs ID/(W/L) has fixed shape

Related VDD insensitive circuits • Filanovsky, etc, “Mutual Compensation of Mobility and Threshold Voltage Temperature Effects with Applications in CMOS Circuits”. • G. Giustolisi “A Low-Voltage Low-Power Voltage Reference Based on Subthreshold MOSFETs”. • Ka Nang Leung “A CMOS Voltage Reference Based on Weighted VGS for CMOS Low-Dropout Linear Regulators”. • Bernhard Boser. “Analog Circuit Design with Submicron Transistors". IEEE SSCS Meeting, Santa Clara Valley, May 2005.

TSMC 0. 18 um Process

TSMC 0. 18 um Process

TSMC 0. 18 um Process

TSMC 0. 18 um Process

TSMC 0. 18 um Process

TSMC 0. 18 um Process